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  • 专利说明
  • 权利要求
  • 类似技术
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    • 专利摘要:
    The invention relates to a switched-mode power supply (14) for supplying the components of a photovoltaic system (1) with a constant DC output voltage (UJ, with connections (15) for connection to the photovoltaic modules (2) of the photovoltaic system (1) for providing a DC input voltage (Ue), comprising a DC-DC converter (16) comprising at least one switch (17), a transformer (18), a control device (22) for controlling the at least one switch (17) with a switching frequency (fs) to obtain the desired DC output voltage (Ua), a Output rectifier (23) and with terminals (24) for providing the DC output voltage (Ua), and an inverter (4) and a strand monitoring (3) of a photovoltaic system (1) to create a low-loss output DC voltage (Ua) in a very wide range the DC input voltage (Ue) between 200V and 1500V is the DC-DC converter (16) by a Ko a combination of barrier and flow transducer with two switches (17, 17 ') arranged in series, the switches (17, 17') being connected to the control device (22), and the control device (22) being designed such that the control of the Output voltage (Ua) is such that the switches (17, 17 ') in response to the primary-side current through the primary winding (20) of the transformer (18) are connected.
    公开号:AT512780A4
    申请号:T50231/2012
    申请日:2012-06-13
    公开日:2013-11-15
    发明作者:
    申请人:Fronius Int Gmbh；
    IPC主号:
    专利说明:

    arirnted: l4-06-2012 .1
    1
    The invention relates to a switching power supply for supplying the components of a photovoltaic system with a constant DC output voltage, with terminals for connection to the photovoltaic photovoltaic modules to provide a DC input voltage in the range between 200V and 1500V, with a DC-DC converter comprising at least one switch, a transformer with a Spool, a primary winding and a secondary winding, a control device for controlling the at least one switch of the DC-DC converter with a switching frequency to achieve the desired DC output voltage, an output rectifier and with terminals for providing the DC output voltage.
    Furthermore, the invention relates to an inverter and a strand monitoring for a photovoltaic system with photovoltaic modules, with a power supply.
    Photovoltaic systems are used to generate electrical energy from light, in particular sunlight, and to feed into supply networks or to use for the operation of electrical consumers. Photovoltaic modules are used to generate DC voltage from light energy. The generated DC voltage is converted into alternating voltage by means of inverters. Recently, the trend has been to use a higher number of photovoltaic modules with correspondingly higher input DC voltages from the lower low voltage range of, for example, 200V to the medium voltage range of, for example, 1500V. For the management of a large number of series and parallel interconnected photovoltaic modules, so-called string controllers are used. In the future, a continuation of the trend towards even more photovoltaic modules or even higher input DC voltages is to be expected.
    To supply the electrical components of the photovoltaic system, in particular the inverter and the possible string monitoring, if this is not integrated in the inverter, are usually circuits for power supply, which from the DC voltage of the photovoltaic modules, the required DC voltage for operating the electrical 2
    Generate components of the photovoltaic system. For use in previous photovoltaic systems with limited input voltage ranges conventional power supplies with relatively good efficiency and relatively low losses could be used. However, with the higher range of DC input voltage of, for example, 200V to 1500V, conventional technologies are no longer able to provide power supply circuits which have low losses and relatively good efficiency at all possible input voltages because, with such a high input voltage range, energy efficiency with switching losses is unsatisfactory and a great deal of effort to cool the switch arises.
    Known voltage supplies for components of grid-connected inverters work with flyback converter topologies, which have the disadvantage that at higher voltages ever higher switching losses occur and the energy efficiency therefore decreases. At voltages near or above the medium voltage, energy-efficient power supply is no longer possible, and the losses incurred in the switches can only be reduced with increased cooling, which in turn increases the overall cost and decreases the overall efficiency.
    Other solutions divide the large input DC voltage range into two or more ranges and use as many serial power supplies or switching power supplies with the same number of transformer windings. However, this increases the circuit complexity and thus the cost.
    The aim of the present invention is to provide an above-mentioned switching power supply and an above-mentioned inverter or a beach monitoring for a photovoltaic system, by which even at a relatively high input DC voltage range of 200V to 1500V efficient and low-loss supply of the components of the photovoltaic system with electrical energy can be achieved. Disadvantages of the prior art should be avoided or at least reduced.
    The object of the invention is achieved by an abovementioned
    ϋ;
    3 tes switching power supply, wherein the DC-DC converter is formed by a combination of blocking and forward converter with two switches arranged in series, wherein the switches are connected to the control device, and the control device is designed such that the regulation of the output voltage is such that the Switch are connected in dependence of the primary-side current through the primary winding of the transformer. The DC converter according to the invention of the switching power supply is formed by a combination of blocking and forward converter in half-bridge arrangement. In the subject switching power supply, the switches are designed so that the lowest possible losses occur, which leads to increase the efficiency of an equipped with this switching power supply inverter. In addition, the control device of the subject switched-mode power supply is connected to the primary side of the transformer of the switched-mode power supply, so that the regulation of the output voltage in dependence on the primary-side current and not in response to the greatly fluctuating input voltage can be done. The switching power supply according to the invention is characterized by low losses and thus a smaller size. Due to the low losses in the switches of the switching power supply, the mounting of heat sinks for cooling the components of the switching power supply or inverter is not required. In particular, the size of the transformer of the switching power supply can be significantly reduced compared to previously used transformers.
    Advantageously, the switches are connected to the primary winding of the transformer.
    For isolated control of the connected to the positive input DC voltage switch, the so-called high-side switch-ters, the control device of the switching power supply preferably includes an optocoupler for controlling this high-side switch. Thus, the control of the high-side switch of the switching power supply is made via optoelectronic devices.
    According to a further feature of the invention, the optocoupler is powered by a bootstrap circuit. By using such a bootstrap circuit to control the switches
    4 of the switching power supply, the highside switch can be switched on for more than 50%.
    The regulating device can be designed to regulate the switching frequency of the switches as a function of the primary-side current through the primary winding of the transformer. In this case, the control of the switching frequency of the switch is thus changed with a constant primary-side current to achieve a constant output voltage of the switching power supply. This regulation is known as Pulse Frequency Mode.
    According to a variant of the switched-mode power supply, the regulating device for regulating the switch-on time of a switch is designed as a function of the primary-side current through the primary winding of the transformer at a constant frequency. In this variant, therefore, the pulse width during which a switch is turned on, regulated.
    In order to meet the high demands on the insulation and the structure of the transformer of the switching power supply and to achieve the smallest possible size of the transformer, various measures are advantageous. First, it is to reduce the parasitic capacitances of the transformer advantageous when the terminals of the primary winding and the terminals of the secondary winding of the transformer are arranged on one side.
    Furthermore, it is advantageous if the distance between the terminals of the primary winding and the distance between the terminals of the secondary winding of the transformer is chosen to be as large as possible, since the highest possible potentials have the greatest distance from each other.
    If an insulation hose is placed over the terminals of the primary winding of the transformer, sufficient clearance and creepage distances are created on the primary side of the transformer, which in turn has a positive effect on the size of the transformer. As a spaghetti is in particular a silicone hose.
    iulii 5
    When the secondary winding of the transformer is constituted by a double counterbalanced banded strand, a fully insulated strand or a fully insulated wire, further improvement in insulation and increase in creepage and clearance can be provided.
    A further improvement can be achieved in that an insulation, in particular a polyester film, is arranged between the primary winding and the secondary winding of the transformer.
    Furthermore, it is advantageous if an insulation, in particular a polyester film, is arranged directly on the bobbin of the transformer.
    By casting the transformer with appropriately suitable material further improvements in the insulation and increases in air and creepage distances can be achieved.
    Advantageously, the switching frequency is 18kHz to 500kHz, preferably 54kHz. When using such high switching frequencies, the size of the transformer can be kept low.
    The switches of the switched-mode power supply are preferably formed by transistors, in particular field-effect transistors. In particular, low-resistance high-voltage transistors, such as silicon carbide MOS-FET or J-FET are particularly suitable.
    If diodes and capacitors of corresponding dimensions are arranged in parallel to the switches of the switched-mode power supply, low-loss switching of the switches (zero voltage switching) can be achieved.
    The object of the invention is also achieved by an above-mentioned inverter for a photovoltaic system and an above-mentioned string monitoring for a photovoltaic system, in which the power supply is formed by a switching power supply according to the above description. By providing a particularly low-loss switching power supply, which is able to printed; 14-06 00:12 ^
    I
    6 even with a very large input voltage range of, for example, 200V to 1500V to provide a constant output voltage for the components of the photovoltaic system, this can also be integrated into the inverter or the strand monitoring. The losses in the transistors are so low due to this mode of the power supply that no heat sink must be mounted.
    The present invention will be explained in more detail with reference to the accompanying schematic drawings. Show:
    Fig. 1 is a schematic block diagram of a photovoltaic system;
    FIG. 2 is a block diagram of an inverter of a photovoltaic system; FIG.
    3 shows a block diagram of a switched-mode power supply for supplying the components of a photovoltaic system;
    4 shows an embodiment of a switched-mode power supply for supplying the components of a photovoltaic system;
    5 shows a schematic time profile of the primary-side current through the transformer of the switched-mode power supply according to FIG. 4;
    FIG. 6 shows an embodiment of the driver for the high-side switch of the switched-mode power supply according to FIG. 4; FIG.
    FIG. 7 shows another embodiment of a driver for the high-side switch of the switched-mode power supply according to FIG. 4; FIG.
    8 shows a further embodiment of a driver for the high-side switch of the switched-mode power supply according to FIG. 4;
    9 shows a plan view of a transformer of a switched-mode power supply for supplying the components of a photovoltaic system; and
    10 shows a sectional view through the transformer of a switched-mode power supply according to FIG. 9.
    By way of introduction, it is stated that identical parts of the exemplary embodiment are given the same reference numerals.
    1 shows a schematic block diagram of a known photovoltaic system 1. The photovoltaic modules 2 of the photovoltaic system 1 are usually connected via a strand monitoring system 3
    7 (string controller), which may also be integrated in an inverter 4, connected to the inverter 4. The inverter 4 generates from the DC voltage of the photovoltaic modules 2 a corresponding AC voltage, which is fed into the supply network 5 and / or used to supply corresponding consumer 6. Typically, many photovoltaic modules 2 are connected in series and in parallel. The components of the photovoltaic system 1, in particular the strand monitoring 3 and the inverter 4, must be supplied with appropriate power supplies 7 with the desired electrical energy, preferably a DC voltage of, for example, 14V. The inverter 4 and / or the strand monitoring 3 generates an internal supply voltage for the electronic components or for the circuit structure, which can be performed via corresponding connection elements also to the outside for additional connectable components. Thus, the voltage necessary for the components of the photovoltaic system 1 is derived directly from the available direct voltage of the photovoltaic modules 2. With a very large input DC voltage range or a very large number of photovoltaic modules 2 connected in series and the resulting high voltage, it becomes very difficult with conventional technologies on switched-mode power supplies to produce the required DC voltage for the components of the photovoltaic system 1 with little loss, ie. with relatively good efficiency, manufacture. The large DC input voltage range results from the fact that the solar radiation changes in the course of a day, that is, after sunrise, the photovoltaic modules 2 deliver less energy than at midday. Furthermore, a large DC input voltage range has the advantage that the number of photovoltaic modules 2 connected in series and in parallel can be made more flexible.
    FIG. 2 shows a structure of a known inverter 4, in detail of an HF inverter. Since the individual components or assemblies and functions of inverters 4 are already known from the prior art, will not be discussed in more detail below.
    The inverter 4 has at least one input DC-DC wall 8 ler 8, a DC link 9 and an output DC-AC converter 10. At the input DC-DC converter 8 one or more parallel and / or series-connected photovoltaic modules 2 are connected. The output of the inverter 4 or of the output DC-AC converter 10 can be connected to a supply network 5, such as a public or private AC network or a multi-phase network, and / or with at least one electrical load 6. For example, a consumer 6 is constituted by an engine, refrigerator, radio, home appliances, etc. Likewise, the consumer 6 can also represent a home care. The individual components of the inverter 4 may be connected via a data bus 11 to a control device 12.
    Preferably, such an inverter 4 serves as a so-called grid-connected inverter 4, whose energy management is then optimized to feed as much energy into the supply network 5. As is known from the prior art, the consumers 6 are supplied via the supply network 5. Of course, a plurality of inverters 4 connected in parallel can also be used. As a result, more energy can be provided for operating the consumers 6.
    This energy is supplied by the photovoltaic modules 2 in the form of a DC voltage, which are connected via at least two terminals 15 to the inverter 4.
    The control device 12 of the inverter 4 is formed for example by a microprocessor, microcontroller or computer. Via the control device 12, a corresponding control of the individual components of the inverter 4, such as the input DC-DC converter 8 or the output DC-AC converter 10, in particular the switching elements arranged therein, are made. In the control device 12 for this purpose, the individual control or control processes are stored by appropriate software programs and / or data or characteristics.
    Furthermore, control elements 13 are connected to the control device 12, by means of which the user can, for example, configure the inverter 4 and / or display operating states or parameters 9-for example by means of light-emitting diodes. The controls 13 are connected for example via the data bus 11 or directly to the control device 12. Such controls 13 are arranged for example on a front of the inverter 4, so that an operation from the outside is possible. Likewise, the controls 13 may also be arranged directly on assemblies and / or modules within the inverter 4.
    3 shows a block diagram of a switched-mode power supply 14 for the inverter 4 and / or the line monitoring 3 or further components of a photovoltaic system 1 for forming a constant DC output voltage U from a DC input voltage Ue in a relatively large range of approximately 200V to 1500V. About two terminals 15, the switching power supply 14 is connected to the photovoltaic modules 2 (not shown). The photovoltaic modules 2 provide a DC input voltage Ue / which is in a very large range of, for example, 200V to 1500V. In a DC-DC converter 16, the DC input voltage Ue is converted into AC voltage with the aid of at least one switch 17 and fed to a transformer 18. The transformer 18 consists of a bobbin 19, a primary winding 20 and at least one secondary winding 21. In an output rectifier 23, the transformed voltage signal is rectified and fed to the terminals 24 for tapping the output DC voltage Ua. With this output DC voltage U *, the components of the photovoltaic system 1 are supplied. Via a control device 22, the at least one switch 17 of the DC-DC converter 16 is controlled such that even with different or fluctuating input DC voltages Ue a constant Ausgangsgeichspannungng Ua can be achieved. In this case, the DC-DC converter 16 of the switched-mode power supply 14 is preferably formed by a combination of blocking and forward converter with two switches 17, 17 'arranged in series, the control device 22 being connected to the primary winding 20 of the transformer 18, in particular via the switches 17, 17', connected is. Likewise, the control device 22 detects the terminals 24, the output voltage Ua, which is kept constant at the desired level. For this purpose, the switches 17, 17 'are switched as a function of the output voltage Ua, so that the primary 10-side current through the primary winding 20 of the transformer 18 is adjusted.
    4 shows a preferred embodiment of a switched-mode power supply 14 for supplying components of a photovoltaic system 1, in particular for use in an inverter 4 and / or a string monitor 3, in which the DC voltage converter 16 is provided by a combination of a flyback converter and a forward converter in a half-bridge arrangement two series-connected switches 17, 17 '(one connected to the positive pole of the input DC voltage so-called high-side switch 17 and connected to the ground so-called low-side switch 17') is formed. The circuit is essentially an asymmetrical duty cycle flyback converter, the mode of operation of which will be described below and with reference to the time diagram of the primary-side current of the transformer 18 according to FIG. During the time interval ti, the switch 17 ', the so-called low-side switch 17' or low-side transistor is switched on and both the magnetizing inductance L * and the leakage inductance Ll of the transformer 18 and the series-connected capacitor CI are switched on charged with energy. Accordingly, the current increases in the time interval tj, with no energy being transmitted to the secondary side of the transformer 18.
    The capacitor C3 is in this case charged and the switch 17 oiiorrüorViol Ί- ci Ή During the period t2, the low-side switch 17 'is turned off. The current commutates into the parallel parasitic or additional capacitor C2, which is thus charged. Thus, there are no turn-off losses, since the switch 17 'is de-energized. The capacitor C2 is then charged up to the input voltage Ue, while the capacitor C3 lying parallel to the high-side switch 17 or high-side transistor is discharged. This means that C2 and C3 are reloaded. For this transfer, the inductors Lm and Ll are discharged and the capacitor Cl charged, whereby the polarity of the transformer 18 on the primary side and secondary side changed Thus, in the next step energy to the secondary side 14τ06ίί, 'm [102012/50231 11 transferred. The time period for the reloading depends on the dimensioning of the capacitors C2 and C3 or the choice of the switches, but is generally very short in relation to the charging and discharging processes of CI. During the time t3, the capacitor C2 is already completely discharged and the current from the inductors Lm and Ll flows through the body diode or a diode connected in parallel of the high-Si-de-switch 17. The high-side switch 17 can now almost free of voltage and thus switched on with low loss. In this case, a circuit with switch 17, capacitor CI and transformer 18 is formed. In this case, the current is transferred from Ln to the secondary side (flyback converter operation) and the current from L1 charges CI .Thus, according to a blocking operation, the transformer acts as a choke The time when the switch 17 must be switched on can be determined by means of voltage measurement at the switch 17 - where nearly zero has to be measured or the diode voltage, or one specifies a fixed dead time in which the capacitances C2 and C3 are safely reloaded.Accordingly, the time is determined by the control device 22. It is essential here that the switch 17 is switched on during the time t3 - essentially also at any time possible - so that energy is transferred.For this purpose, the current continues to flow in the same direction.
    As a result of the energy transmission, the current on the primary side decreases until the voltage across the capacitor C1 is greater than the voltage on the secondary side of the transformer 18 times the transmission ratio of the transformer 18 and the entire primary leakage inductance L1 in the transformer 18 is discharged or transmitted.
    Subsequently, the current through the primary winding 20 of the transformer 18 changes its polarity and the energy from the capacitor Cl is transferred via the transformer 18 in the flux mode (forward converter) during the time t4. This in addition to the blocking operation, since the switch 17 'is turned off. The condition for this is that the voltage across the capacitor Cl is greater than the voltage Ua on the secondary side of the transformer 18 multiplied by the transmission ratio ü of the 12th
    Transformers 18, So it is so long transferred energy until CI and Ue * ü are the same.
    The time until the capacitor Cl has discharged to said voltage Ua * ü is determined by the resonance formula t = pi * V (Ll * C1). If this time is longer than t4, the DC-DC converter 16 is not operated gaping. If the time is shorter, Cl is fully discharged to Ua * ü (which corresponds to the so-called lopsided operation of the DC-DC converter 16) and the remaining time until switching is used to reverse the magnetization of the inductance Lm. This is an advantage in the case of higher voltages according to the present invention, since more energy is then available during the oscillation during t5. During the time t5, the highside switch 17 is turned off lossless, since the capacitor C3 is discharged since the time t2. This is because the current is communicated to the capacitor C3. For the subsequent turn-on of the switch 17 ', it is necessary to charge the capacitor C3 and to discharge the capacitor C2. This is done essentially automatically by turning off the switch 17. Subsequently, the switch 17 'loss of the control device 22 are turned on. In non-latching operation, only the primary leakage inductance L1 and, negligibly, the magnetizing inductance Lm drives the current and charges the capacitor C3 and discharges the capacitor C2. In the intermittent operation, the proportion of the magnetizing inductance L "is considerably more involved. During the short time ts, therefore, the capacitors C2 and C3 are recharged equivalently to the time t2. For the transshipment process corresponding energy is required.
    At the beginning of the time t6, the capacitor C2 is already almost completely discharged and the body diode of the low-side switch 17 'or a parallel diode carries the current. The low-side switch 17 'can thus be switched on almost without voltage and thus low loss. The point in time at which the switch 17 'can be switched on with low loss can be determined by measuring the voltage at the switch 17' or by a fixed time in which the capacitor 13 is reliably discharged. Accordingly, turning on the switch 17 'is equivalent to turning on the switch 17 in the time t3.
    This procedure is repeated accordingly with a switching frequency in the range of 18kHz to 500kHz, especially 54kHz. In summary, it can therefore be said that during the time t3 energy is transmitted in the blocking mode and during the time t4 energy is transmitted in flow mode and blocking mode. As a result, stop and forward transducers are combined. This results in accordance with the desired output voltage Ua of the power supply, for example, 5V, 12V, 24V, etc.
    The control of the high-side switch 17 turns out to be not so trivial, since it is turned on for more than 50% (from time t3 to t4). At higher voltages or in case of a soft start, it is even switched on for up to 90% or even longer. The control by means of magnetic transformer is therefore not appropriate, since the demagnetization of the transformer requires relatively high voltages. Therefore, this is preferably an optical control with auxiliary supply, which can be realized either by an auxiliary power supply, or by a bootstrap circuit.
    6 shows a variant of the control of the high-side switch 17 of the DC-DC converter 16 of the switched-mode power supply 14 with a boost circuit. The high-side switch 17 is turned on with the power from the bootstrap capacitor CBS. This is always charged when the low-side switch 17 'is turned on. For very short turn-on periods, as they occur especially at high voltages, this charge must be done in a very short time. IGBT's (Insulated Gate Bipolar Transistor) are for this purpose as a switch 17, 17 'is not suitable because the saturation voltage is reached relatively late, which is why the bootstrap capacitor CBs is not fully charged and the voltage is not sufficient to the high-side switch 17th head for. Better suited here are low-resistance MOS-FETs or J-FETs, for example based on silicon carbide. Here one can simply calculate the time required to charge the bootstrap capacitor CBs with the resistor RCSon of the low-side switch 17 '14 with t = RDSon * CBS and UCbs = Uq * (1-θλ (-t / T)), where Uq in this case is 15V minus the forward voltage of the diode. In this case, the 15V correspond to the supply voltage of the control device 22 for generating the highside signal HS and lowside signal LS. To achieve isolation from the ground potential, the control of the switch 17 is formed by an optocoupler 25, since switch 17 has no ground potential.
    Fig. 7 shows a variant of the control of the switch 17 with an auxiliary supply Ux, which is supplied for example by a battery or an auxiliary power supply.
    Another possibility for a safe control is to change the topology so that the high-side switch 17 does not reach over 50% duty cycle. Then one can resort to known from the prior art magnetic coupler 27 for driving the high-side switch 17 (see Fig. 8). For this purpose, according to the functional description of FIGS. 2 to 7, the switches are reversed. Thus, the switch 17 'assumes the function of the switch 17, thus has a reference to ground and can be controlled directly by the controller 22. This has the consequence that the duty cycle is no longer relevant and according to the magnetic coupler 27 can be used.
    One way of regulation by the controller 22 of the output voltage üa is to control the time ti at a constant switching frequency fs. The scheme can be done basically two known methods. In "Current Mode" the current amplitude is regulated during ti as a function of the output voltage Ua. When starting up, when the secondary capacitor is still discharged, the primary current is slowly increased until the output voltage Ua is reached. The advantage of this regulation is first and foremost the fact that just when starting up compared to the "Voltage Mode". no large primary overcurrents occur. In "Voltage Mode" the pulse width is regulated during tx. When starting up this step by step apart. This has the disadvantage that at even lower secondary voltage, the energy stored in the transformer 18, can not be discharged fast enough, and it remains a ü
    IS
    Mm 15
    Most of the energy in the transformer 18. Thus, the primary current at the next period starts at approximately the value at which it was turned off at the last period. Thus, the current continues to increase, and there is a risk that the transformer 18 saturates. Remedy can be provided with a current limiting, which turns off the switch 17, which conducts during ti, at a defined current and here in the "Current Mode". passes.
    Another possibility is the regulation of the frequency fs with constant time ti. This is known as "Pulse Frequency Mode". In this case, t4 is extended with decreasing load, so that the number of energy transfers decreases. At the same time, the capacitor CI connected in series with the transformer 18 also discharges deeper, and more reactive power is needed to transfer energy.
    At high voltages, the requirements for the insulation and the structure of the transformer 1 are enormous. On the one hand, the energy which is required for the oscillation is directly proportional to the parallel parasitic capacitance of the transformer 18.
    In order to keep the capacitive influences as low as possible, the transformer 18 is constructed so that a winding can always be fully developed in one layer. Alternatively, an odd number of layers can be used for the winding. This ensures that the highest possible potentials have the greatest distance from each other. In addition, care was taken to ensure that the winding start and the winding end of the winding also have a large distance from each other. This principle is applied to both the primary winding 20 and the secondary winding 21.
    The continuous load due to the high input voltage Ue of, for example, 1500V place very high demands on the insulation of the transformer 18.
    For this purpose, the terminals of the primary winding 20 and the secondary winding 21 are arranged on the same pin row due to the capacitive optimization measures. Care must be taken here
    PjMj 16tpr ^ ted: ϊΐ # -06 ^ -2012 fE014.1 ^ 10 2012/50231 that those connections, which lie directly in the separation distance between primary winding 20 and secondary winding 21, be pulled out of the bobbin 19- Of course, the distance be chosen between the terminals also large enough.
    On the terminals of the primary winding 20, a silicone tube 26 is preferably arranged so that sufficient air and creepage distances are created. On the secondary side and on the primary side, a double counterbalanced banded wire is used. By this double counter equalization at 50% film overlap an air gap and creepage distance of 1.5 times the insulating film width is achieved. Alternatively, a fully insulated wire or a fully insulated wire can be used. In addition, a lateral distance between the side wall of the bobbin 19 and the windings 20, 21 is maintained. Between the primary winding 20 and the secondary winding 21, a sufficiently thick layer of polyester film is inserted, since this represents the direct point of separation. Directly on the bobbin 19 is preferably also wrapped a layer of polyester film, because polyester has a higher dielectric strength than the material of the bobbin 19. The silicone tubes 26 which are striped over the terminals of the primary winding 20 must reach to the Pinkontaktierung, otherwise possibly over the ferrite core the air and creepage distances could be shortened. Finally, a Vollverguß the transformer 18 is recommended.
    With these measures, the air and creepage distances can be stretched so that operation at high input voltages Ue can be guaranteed in the long term on a transformer 18 of a switching power supply 14 with very small dimensions.
    The illustrated sketches according to FIGS. 9 and 10 of a transformer 18 represent only one embodiment.
    权利要求:
    Claims (17)
    [1]
    17 17 141 14 ^ 06 ^ 2012 Claims: 1. Switching power supply (14) for supplying the components of a photovoltaic system (1) with a constant DC output voltage (UJ, with terminals (15) for connection to the photovoltaic modules (2) of the photovoltaic system ( 1) for providing a DC input voltage (Ue) in the range between 200V and 1500V, comprising a DC-DC converter (16) comprising at least one switch (17), a transformer (18) with a bobbin (19), a primary winding (20) and a secondary winding (21), a control device (22) for controlling the at least one switch (17) of the DC-DC converter (16) with a switching frequency (fs) to obtain the desired DC output voltage (UJ, an output rectifier (23) and with terminals (24) for providing the DC output voltage (Ua), characterized in that the DC-DC converter (16) by a combination of blocking and forward converter with two in Series arranged switches (17, 17 ') is formed, wherein the switches (17, 17') are connected to the control device (22), and the control device (22) is designed such that the regulation of the output voltage (Ua) takes place in such a way in that the switches (17, 17 ') are connected as a function of the primary-side current through the primary winding (20) of the transformer (18).
    [2]
    Second switching power supply (14) according to claim 1, characterized in that the switches (17, 17 ') to the primary winding (20) of the transformer (18) are connected.
    [3]
    3. Switching power supply (14) according to claim 1 or 2, characterized in that the control device (22) includes an optocoupler (25) for driving a switch (17), the so-called high-side switch contains.
    [4]
    4. Switching power supply (14) according to claim 3, characterized in that the optocoupler (25) is powered by a bootstrap circuit.
    [5]
    5. Switching power supply (14) according to one of claims 1 to 4, characterized in that the control device (22) for regulating the

    fPrinted:, 14-06-2012 18 switching frequency (fs) of the switches (17, 17 ') is formed as a function of the primary-side current through the primary winding (20) of the transformer (18).
    [6]
    6. Switching power supply (14) according to one of claims 1 to 5, characterized in that the control device (22) for controlling the switch-on time (tx) of a switch (17) in dependence of the primary-side current through the primary winding (20) of the transformer (18 ) is trained.
    [7]
    7. Switching power supply (14) according to one of claims 1 to 6, characterized in that the terminals of the primary winding (20) and the terminals of the secondary winding (21) of the transformer (18) are arranged on one side. ß. Switching power supply (14) according to one of claims 1 to 7, characterized in that the distance between the terminals of the primary winding (20) and the distance of the terminals of the secondary winding (21) of the transformer (18) is as large as possible.
    [8]
    9. Switching power supply · (14) according to any one of claims 1 to 8, characterized in that above the terminals of the primary winding (20) an insulation tube (26), in particular a silicone tube, is arranged.
    [9]
    10. Switching power supply (14) according to one of claims 1 to 9, characterized in that the secondary winding (21) is formed by a double counterbalanced banded stranded wire, a fully insulated stranded wire or a fully insulated wire.
    [10]
    11. Switching power supply (14) according to one of claims 1 to 10, characterized in that between the primary winding (20) and the secondary winding (21) of the transformer (18) an insulation, in particular a polyester film is arranged.
    [11]
    12. Switching power supply (14) according to any one of claims 1 to 11, characterized in that directly on the bobbin (19) of the transformer (18) an insulation, in particular a polyester film is arranged.
    [12]
    13. Switching power supply (14) according to any one of claims 1 to 12, da-characterized in that the transformer (18) is encapsulated.
    [13]
    14. Switching power supply (14) according to any one of claims 1 to 13, characterized in that the switching frequency (fs) 18kHz to 500kHz, preferably 54kHz.
    [14]
    15. Switching power supply (14) according to one of claims 1 to 14, characterized in that the switches (17, 17 ') by transistors, in particular field effect transistors, are formed.
    [15]
    16. Switching power supply · (14) according to one of claims 1 to 15, characterized in that parallel to the switches (17, 17 ') diodes and capacitors are arranged.
    [16]
    17. Inverter (4) for a photovoltaic system (1) with photovoltaic modules (2), with a voltage supply (7), characterized in that the voltage supply (7) by a switching power supply (14) according to one of claims 1 to 16 formed is.
    [17]
    18. strand monitoring (3) for a photovoltaic system (1) with photovoltaic modules (2), with a voltage supply (7), characterized in that the voltage supply (7) by a switching power supply (14) is designed according to one of claims 1 to 16.
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    同族专利:
    公开号 | 公开日
    WO2013185159A2|2013-12-19|
    CN104756386B|2018-02-13|
    WO2013185159A3|2014-09-04|
    DE112013002982A5|2015-03-19|
    AT512780B1|2013-11-15|
    US20150171755A1|2015-06-18|
    US9800160B2|2017-10-24|
    CN104756386A|2015-07-01|
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    法律状态:
    优先权:
    申请号 | 申请日 | 专利标题
    ATA50231/2012A|AT512780B1|2012-06-13|2012-06-13|Switching power supply and inverter and strand monitoring with such a switching power supply|ATA50231/2012A| AT512780B1|2012-06-13|2012-06-13|Switching power supply and inverter and strand monitoring with such a switching power supply|
    US14/407,597| US9800160B2|2012-06-13|2013-06-11|Switched mode power supply, inverter and string monitoring assembly comprising said type of switched mode power supply|
    PCT/AT2013/050117| WO2013185159A2|2012-06-13|2013-06-11|Switched mode power supply, inverter and string monitoring assembly comprisng said type of switched mode power supply|
    CN201380040508.8A| CN104756386B|2012-06-13|2013-06-11|The inverter and group string monitor component of switched-mode power supply and switched-mode power supply including the type|
    DE112013002982.0T| DE112013002982A5|2012-06-13|2013-06-11|Switching power supply and inverter and strand monitoring with such a switching power supply|
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